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ISL59830A
Data Sheet September 26, 2006 FN6233.3
True Single Supply Video Driver With Power Down
The ISL59830A is a revolutionary device that allows true single-supply operation of video amplifiers. The device runs off a single 3.3V supply and generates the required negative voltage internally. This allows for DC-accurate coupling of video onto a 75 double-terminated line. Since the buffers have an integrated 6dB gain, the only external components required are the 75 termination resistors and a small capacitor. An input reference voltage can be supplied to shift the analog video level down by an amount equal to the reference (typically 0.6V).
Features
* Triple single-supply buffer * Operates from single +3.3V supply * No output DC blocking capacitor needed * Fixed gain of 2 output buffer * Output three-statable * Enable/disable function * Charge pump power down function * 50MHz 0.1dB bandwidth * 200MHz -3dB bandwidth
Ordering Information
PART NUMBER ISL59830AIAZ (See Note) PART MARKING 59830AIAZ TAPE & REEL 13" PACKAGE PKG. DWG. #
* Pb-free plus anneal available (RoHS compliant)
Applications
* Driving video
16 Ld QSOP M16.15A (Pb-free) 16 Ld QSOP M16.15A (Pb-free)
ISL59830AIAZ-T7 59830AIAZ (See Note)
Pinout
ISL59830A (16 LD QSOP) TOP VIEW
RIN 1 GIN 2 BIN 3 REF 4 VEE 5 GND 6 VEEOUT 7 DGND 8 16 ROUT 15 GOUT 14 BOUT 13 VCC 12 EN 11 VCC 10 PD 9 DVCC
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright (c) Intersil Americas Inc. 2006. All Rights Reserved. All other trademarks mentioned are the property of their respective owners.
ISL59830A
Absolute Maximum Ratings (TA = +25C)
VCC, Supply Voltage between VS and GND5V VIN, VREF . . . . . . . . . . . . . . . . . . . . . . . . . . . .VCC+0.3V, VEE-0.3V Voltage between VIN and VREF . . . . . . . . . . . . . . . . . . . . . . . . . .2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 30mA Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40C to +85C Maximum Die Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . +150C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65C to +150C Lead Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +260C Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
AC Electrical Specifications
PARAMETER BW -3dB
VCC = DVCC = +3.3V, REF = GND, TA = +25C, RL = 150, unless otherwise specified. CONDITIONS VOUT = 200mVPP VOUT = 2VPP MIN TYP 200 100 50 500 .06 0.1 6MHz 6MHz -90 -70 20 168 IEE = 0mA to 10mA 12 30 VCC = DVCC = +3.3V, REF = GND, TA = +25C, RL = 150, unless otherwise specified. CONDITIONS MIN 3.0 RL = 150, VIN = +2.5V to -1V RL = 150 VIN = 0V to 1.5V VREF = 0 RL = 10, VIN = 1.2V RL = 10, VIN = -0.3V Enabled Three-stated 1 10 60 Enabled EN = PD = 3.3V 4 0.9 5 6 90 150 1.0 -25 50 -18 0.5 1.7 7 15 +25 TYP MAX 3.6 1.5 UNIT V % % M mV mA mA M dB mA mA k 60 MAX UNIT MHz MHz MHz V/s % dB dB nV/Hz MHz mV mV
DESCRIPTION 3dB Bandwidth
BW 0.1dB SR dG dP XT I VN CSW Freq Load Reg VRIPPLE
0.1dB Bandwidth Slew Rate Differential Gain Differential Phase Hostile Crosstalk Input to Output Isolation Input Noise Voltage Charge Pump Switch Frequency
VOUT = 2VPP VOUT = 2VPP
Ripple Voltage
DC Electrical Specifications
PARAMETER V+ VG% GM RIN VOS IOUT + IOUT ZOUT
DESCRIPTION Supply Range Gain Error Gain Matching Input Resistance Output Offset Voltage Output Current Output Current Output Impedance
PSRR IS IS_PD RREF
Power Supply Rejection Ratio Supply Current Power Down Supply Current Input Reference Resistor
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FN6233.3 September 26, 2006
ISL59830A Pin Descriptions
PIN NUMBER 1 PIN NAME RIN PIN FUNCTION Analog input EQUIVALENT CIRCUIT
VCC
VEE CIRCUIT 1
2 3 4
GIN BIN REF
Analog input Analog input Reference input
Reference Circuit 1 Reference Circuit 1
VCC RIN GIN BIN 3 ROUT GOUT BOUT
+ -
REF
VEE CIRCUIT 2
5
VEE
Chip substrate
VCC
VEE OUT -+
DVCC CHARGE PUMP DGND CIRCUIT 3
VEE
6 7 8 9 10 11, 13 12
GND VEE OUT DGND DVCC PD VCC EN
Analog ground Charge pump output Charge pump ground Charge pump supply voltage Charge pump enable Positive power supply Chip enable
VCC
Reference Circuit 3 Reference Circuit 3 Reference Circuit 3 Reference Circuit 4
VEE CIRCUIT 4
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FN6233.3 September 26, 2006
ISL59830A Pin Descriptions (Continued)
PIN NUMBER 14 PIN NAME BOUT PIN FUNCTION Analog output EQUIVALENT CIRCUIT
VCC
VEE CIRCUIT 5
15 16
GOUT ROUT
Analog output Analog output
Reference Circuit 5 Reference Circuit 5
Typical Performance Curves
3 2 1 0 500 -1 -2 -3 1M 150 75 10M 100M 1G -5 100K 1M 10M FREQUENCY (Hz) 100M 1G AV=+2 CL=0pF NORMALIZED GAIN (dB) 3 5 AV=+2 RL=500 9pF 4.7pF 2.2pF 1 0pF
NORMALIZED GAIN (dB)
1k
-1
-3
FREQUENCY (Hz)
FIGURE 1. GAIN vs FREQUENCY FOR VARIOUS RLOAD
FIGURE 2. GAIN vs FREQUENCY FOR VARIOUS CLOAD
5 NORMALIZED OUTPUT (dB) 0 -5 -10 -15 -20 -25 -30 -35 1 100 200 300 400 500 FREQUENCY (MHz) AV=+2 CL=0pF RL=500
300 AV=+2 RL=500 GAIN ROLL-OFF (MHz) 240 -3dB ROLL-OFF
180
120
60 -0.1dB ROLL-OFF 0 2.25 2.8 3.35 3.9 4.45 5
SUPPLY VOLTAGE (V)
FIGURE 3. VREF PIN OUTPUT FREQUENCY RESPONSE
FIGURE 4. GAIN ROLL-OFF vs FREQUENCY
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FN6233.3 September 26, 2006
ISL59830A Typical Performance Curves (Continued)
-30 AV=+2 -40 RL=500 -50 CROSS TALK (dB) -60 -70 -80 -90 -100 -110 -120 100K 1M 10M FREQUENCY (Hz) 100M 1G DISABLED ENABLED ISOLATION (dB) -20 AV=+2 -30 RL=500 -40 -50 -60 -70 -80 -90 -100 100K 1M 10M FREQUENCY (Hz) 100M 1G DISABLED ENABLED
FIGURE 5. CROSS TALK CHANNEL TO CHANNEL (TYPICAL)
FIGURE 6. INPUT TO OUTPUT ISOLATION vs FREQUENCY
120 100 80 60 40 20 0 1 1.5 2 2.5 3 3.5 SUPPLY VOLTAGE (V) AV=+2 RL=500
200 -3dB 160 BANDWIDTH (MHz) AV=+2 RL=500
SUPPLY CURRENT (mA)
120
80
40 -0.1dB 0 27 47.5 68 88.5 109 129.5 150
TEMPERATURE (C)
FIGURE 7. SUPPLY CURRENT vs SUPPLY VOLTAGE
FIGURE 8. BANDWIDTH vs TEMPERATURE
95 AV=+2 RL=500 SUPPLY CURRENT (mA) 90 IMPEDANCE ()
100
10
85
1
80
0.1
75 27
55.6
84.2
112.8
141.4
170
0.01 10K
100K
1M FREQUENCY (Hz)
10M
100M
TEMPERATURE (C)
FIGURE 9. SUPPLY CURRENT vs TEMPERATURE
FIGURE 10. OUTPUT IMPEDANCE vs FREQUENCY
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FN6233.3 September 26, 2006
ISL59830A Typical Performance Curves (Continued)
-10 VOLTAGE NOISE (nV/Hz), CURRENT NOISE (pA/Hz) 1K
-30 PSRR (dB)
100
-50 PSRR-70 PSRR+ -90
10
eN
1
IN+ IN-
-110 1K
10K
100K
1M
10M
100M
0.1 10
100
1K
10K
100K
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 11. POWER SUPPLY REJECTION RATIO vs FREQUENCY
FIGURE 12. VOLTAGE AND CURRENT NOISE vs FREQUENCY
-30 HARMONIC DISTORTION (dBc) -40 -50 -60 -70 -80 -90 -100 0 10 20 30 40 FUNDAMENTAL FREQUENCY (MHz) 3RD HD 2ND HD THD
-30 -40 -50 THD (dBc) -60 -70 -80 -90 0.5 THD FIN=1MHz 1 1.5 2 2.5 3 3.5 THD FIN=10MHz
OUTPUT VOLTAGE (VP-P)
FIGURE 13. HARMONIC DISTORTION vs FREQUENCY
FIGURE 14.
DIFFERENTIAL GAIN (%)
0 -0.02 -0.04 -0.06 -0.08 IRE
DIFFERENTIAL PHASE ()
0 -0.02 -0.04 -0.06 -0.08 IRE
FIGURE 15. DIFFERENTIAL GAIN
FIGURE 16. DIFFERENTIAL PHASE
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FN6233.3 September 26, 2006
ISL59830A Typical Performance Curves (Continued)
VOLTS (500mV/DIV)
VOLTS (500mV/DIV)
TIME (200ns/DIV)
TIME (200ns/DIV)
FIGURE 17. DISABLE TIME
FIGURE 18. ENABLE TIME
TIME (10ns/DIV)
VOLTS (500mV/DIV)
VOLTS (50mV/DIV)
TIME (10ns/DIV)
FIGURE 19. SMALL SIGNAL RISE & FALL TIME
FIGURE 20. LARGE SIGNAL RISE & FALL TIMES
3.25
OUTPUT RANGE (V)
VOLTS (10mV/DIV)
3
2.75
2.5 50 TIME (20ns/DIV)
AV=+2 CL=3.9pF 250 450 650 850 1050
LOAD RESISTANCE ()
FIGURE 21. CHARGE PUMP OSCILLATION
FIGURE 22. MAXIMUM OUTPUT MAGNITUDE vs LOAD RESISTANCE
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FN6233.3 September 26, 2006
ISL59830A Typical Performance Curves (Continued)
1.6 BACKDRIVE CURRENT (mA) BACKDRIVE ACROSS 5 RESISTOR TYPICAL CHANNEL 1.2 PEAKING (dB) 1.2 1.6 AV=+2 RL=500 CL=3.9pF
0.8
0.8
0.4
0.4
0 0 1 2 3 4 5 BACKDRIVE VOLTAGE (V)
0 2.2
2.4
2.6
2.8
3
3.2
3.4
3.6
3.8
4
SUPPLY VOLTAGE (V)
FIGURE 23. BACKDRIVE VOLTAGE vs CURRENT
FIGURE 24. PEAKING vs SUPPLY VOLTAGE
JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1.4 POWER DISSIPATION (W) POWER DISSIPATION (W) 1.2 1 791mW 0.8 0.6 0.4 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (C)
J QS OP 16 A =1 58 C /W
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1.8 1.6 1.4 1.2 1 0.8 0.6 0.4 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (C) 1.116W
J QS OP 16 C /W
A =1
12
FIGURE 25. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
FIGURE 26. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
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FN6233.3 September 26, 2006
ISL59830A Block Diagram
VCC
Y
RIN
+ 6dB -
ROUT
REFERENCE GIN
Pb
+ 6dB -
GOUT
Pr
BIN
+ 6dB -
BOUT DVCC
CHARGE PUMP VEE VOUT = 2VIN - VREFERENCE
VEE-OUT
Demo Board Schematic
RED_IN R1 75 RED_OUT GREEN_IN R2 75 1 RIN 2 GIN 3 BIN BLUE_IN R3 75 R4 VCC 499 R8 1k VCC REFERENCE CONTROL C2 0.1F D1 1N4148
(or similar)
ROUT 16 GOUT 15 BOUT 14 VCC 13 EN 12 VCC 11 PD 10 DVCC 9 C5 0.1F
R4 R5 R6
75 75 GREEN_OUT 75 VCC C3 0.1F VCC
C4 1.0F
R7 1k
4 REF 5 VEE 6 GND 7 VEEOUT 8 DGND
BLUE_OUT
2
1 3
DISABLE ENABLE
Option: Panasonic 120 Bead EXC3BP121H Lower Amp output noise from charge pump
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FN6233.3 September 26, 2006
ISL59830A + DC-Restore Solution
1 IN1 2 COM1 3 NC1
IN2 16 COM2 15 NC2 14 V+ 13 NC 12 NC3 11 COM3 10 IN3 9 R9 2k R10 2k 1 RIN ROUT 16 GOUT 15 BOUT 14 VCC 13 EN 12 VCC 11 NC 10 DVCC 9 C15 R4 R5 R6 75 75 75 VCC C1 0.1F C14 20pF C13 20pF Pb
10
YO R1 75 Pb R2 75 C4 C5 C6 Pr R3 75 R11 499 REF MMBP 3904 R8 VCC
FN6233.3 September 26, 2006
R7 2k
4 V5 GND 6 NC4 7 COM4 8 IN4
(No Connect)
ISL43140
CN = Option for lower charge pump noise
C12 20pF YO
0.1F 0.1F 2 GIN 0.1F 3 BIN 4 REF VEE (-1.6V) 1k R12 5 VEE 6 GND
ISL59830A
C7 1.0F
Pr
REFERENCE CONTROL
D1 1N4148
(or similar)
C11 0.1F
7 VEEOUT 8 DGND
ENABLE 2 1 0.1F 3
VCC VCC GND + C16 1F
VCC
ISL59830 1 COMP C4 0.1F 2 COMP
SYNC OUT VIDEO IN VDD 8 OUT 7 RESET 6 BACK PORCH 5 OUT
C8 0.1F
Option: Panasonic 120 Bead EXC3BP121H Lower Amp output noise from charge pump
R13 681k
3 VSYNC OUT C10 0.1F 4 GND
C9 0.1F
EL1881
ISL59830A Description of Operation and Application Information Theory Of Operation
The ISL59830A is a highly practical and robust marriage of three high bandwidth, high speed, low power, rail-to-rail voltage feedback amplifiers with a charge pump, to provide a negative rail without an additional power supply. Designed to operate with a single supply voltage range of from 0V to 3.3V, the ISL59830A eliminates the need for a split supply with the incorporation of a charge pump capable of generating a bottom rail as much as 1.6V below ground; for a 4.9V range on a single 3.3V supply. This performance is ideal for NTSC video with its negative-going sync pulses. distortion, low power, and high frequency amplifier capable of driving moderately capacitive loads with near rail-to-rail performance.
Input Output Range
The three amplifier channels have an input common mode voltage range from 0.15V below the bottom rail to within 100mV of the positive supply, VS+ pin (Note: bottom rail is established by the charge pump at negative one half the positive supply). As the input signal moves outside the specified range, the output signal will exhibit increasingly higher levels of harmonic distortion. And of course, as load resistance becomes lower, the current drive capability of the device will be challenged and its ability to drive close to each rail is reduced. For instance, with a load resistance of 1k the output swing is within 100mV of the rails, while a load resistance of 150 limits the output swing to within around 300mV of the rails.
The Amplifier
The ISL59830A fabricated on a dielectrically isolated high speed 5V Bi-CMOS process with 4GHz PNPs and NPN transistor exceeding 20GHz - perfect for low distortion, low power demand and high frequency circuits. While the ISL59830A utilizes somewhat standard voltage mode feedback topologies, there are many non-standard analog features providing its outstanding bandwidth, rail-to-rail operation, and output drive capabilities. The input signal initially passes through a folded cascode, a topology providing enhanced frequency response essentially by fixing the base collector voltage at the junction of the input and gain stage. The collector of each input device looks directly into an emitter that is tied closely to ground through a resistor and biased with a very stable DC source. Since the voltage of this collector is "locked stable" the effective bandwidth limiting of the Miller capacitance is greatly reduced. The signal is then passed through a second fullyrealized differential gain stage and finally through a proprietary common emitter output stage for improved railto-rail output performance. The result is a highly-stable, low
Amplifier Output Impedance
To achieve near rail-to-rail performance, the output stage of the ISL59830A uses transistors in the common emitter configuration, typically producing higher output impedance than the standard emitter follower output stage. The exceptionally high open loop gain of the ISL59830A and local feedback reduces output impedance to less than 2 at low frequency. However, since output impedance of the device is exponentially modulated by the magnitude of the open loop gain, output impedance increases with frequency as the open loop gain decreases with frequency. This inductive-like effect of the output impedance is countered in the ISL59830A with proprietary output stage topology, keeping the output impedance low over a wide frequency range and making it possible to easily and effectively drive relatively heavy capacitive loads (See Figure 10).
IN+
INOUT
BIAS
FIGURE 27.
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FN6233.3 September 26, 2006
ISL59830A
The Charge Pump
The ISL59830A charge pump provides a bottom rail up to 1.65V below ground while operating on a 0V to 3.3V power supply. The charge pump is internally regulated to one-half the potential of the positive supply. This internal multi-phase charge pump is driven by a 160MHz differential ring oscillator driving a series of inverters and charge storage circuitry. Each series inverter charges and places parallel adjoining charge circuitry slightly out of phase with the immediately preceding block. The overall effect is sequential discharge and generation of a very low ripple of about 10mV that is applied to the amplifiers providing a negative rail of up to -1.65V. There are two options to reduce the output supply noise. * Add a 120 bead in series between VCC and DVCC to further reduce ripple. * Add a 20pF capacitor between the back load 75 resistor and ground (see the ISL59830A + DC-Restore Solution schematic on page 10). amp +input gain change. Offset on the VREF pin must be low impedance to prevent gain error and cross talk. A transistor emitter follower should work like an NPN MMBT3904 with the emitter connected to the VREF pin and 1k pull down to V- with 1F cap bypass to ground and the collector to V+ and base to V offset source. If better tempco is needed then a diode may be used in series with the pot to ground. A 499W resistor may be added in series with the collector to prevent damage when testing. See the Block Diagram on page 9.
The VEE Pin
The VEE pin is the output pin for the charge pump. A voltmeter applied to this pin will display the output of the charge pump. This pin does not affect the functionality of the part. One may use this pin as an additional voltage source. Keep in mind that the output of this pin is generated by the internal charge pump and a fully regulated supply that must be properly bypassed. We recommend a 0.1F ceramic capacitor placed as close to the pin and connected to the ground plane of the board.
Input, Output, and Supply Voltage Range
The ISL59830A is designed to operate with a single supply voltage range of from 0V to 3.3V. The need for a split supply has been eliminated with the incorporation of a charge pump capable of generating a bottom rail as much as 1.6V below ground, for a 4.9V range on a single 3.3V supply. This performance is ideal for NTSC video with its negative-going sync pulses.
VOLTS (10mV/DIV)
Video Performance
TIME (20ns/DIV)
FIGURE 28. CHARGE PUMP OSCILLATION
The system operates at sufficiently high frequencies that any related charge pump noise is far beyond standard video bandwidth requirements. Still, appropriate bypassing discipline must be observed, and all pins related to either the power supply or the charge pump must be properly bypassed. See "Power Supply Bypassing and Printed Circuit Board Layout" in this section.
The VREF Pin
Applying a voltage to the VREF pin simply places that voltage on what would usually be the ground side of the gain resistor of the amplifier, resulting in a DC-level shift of the output signal. Applying 100mV to the Vref pin would apply a 100mV DC level shift to the outgoing signal. The charge pump provides sufficient bottom room to accommodate the shifted signal. Note: The VREF input is the common point of the 3 amps minus input resistors. Any common resistance on VREF input will share the voltage induced on it with all the other amps, so using a resistor source to get offset will cause cross talk and gain change for the offset for all amps and 12
For good video performance, an amplifier is required to maintain the same output impedance and the same frequency and phase response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150 because of the change in output current with changing DC levels. Special circuitry has been incorporated into the ISL59830A for the reduction of output impedance variation with the current output. This results in outstanding differential gain and differential phase specifications of 0.06% and 0.1, while driving 150 at a gain of +2. Driving higher impedance loads would result in similar or better differential gain and differential phase performance.
NTSC
The ISL59830A, generating a negative rail internally, is ideally suited for NTSC video with its accompanying negative-going sync signals; easily handled by the ISL59830A without the need of an additional supply as the ISL59830A generates a negative rail with an internal charge pump referenced at negative 1/2 the positive supply.
YPbPr
YPbPr signals originating from a DVD player requiring three channels of very tightly-controlled amplifier gain accuracy present no difficulty for the ISL59830A. Specifically, this
FN6233.3 September 26, 2006
ISL59830A
standard encodes sync on the Y channel and it is a negativegoing signal; easily handled by the ISL59830A without the need of an additional supply as the ISL59830A generates a negative rail placed at negative 1/2 the positive supply. Additionally, the Pb and Pr are bipolar analog signals and the video signals are negative-going; and again easily handled by the ISL59830A. exceeded and the part will be damaged. This limit is set by the design of the internal metal interconnections.
Power Dissipation
With the high output drive capability of the ISL59830A, it is possible to exceed the +150C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for an application to determine if load conditions or package types need to be modified to assure operation of the amplifier in a safe operating area. The maximum power dissipation allowed in a package is determined according to:
T JMAX - T AMAX PD MAX = ------------------------------------------- JA
Driving Capacitive Loads and Cables
The ISL59830A, internally-compensated to drive 75 cables, will drive 10pF loads in parallel with 1k with less than 5dB of peaking. If less peaking is required, a small series resistor, usually between 5 to 50, can be placed in series with the output. This will reduce peaking at the expense of a slight closed loop gain reduction. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, a back-termination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a backtermination resistor. Again, a small series resistor at the output can help to reduce peaking. The ISL59830A is a triple amplifier designed to drive three channels; simply deal with each channel separately as described in this section.
Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature JA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: for sourcing:
V OUT i PD MAX = V S x I SMAX + ( V S - V OUT i ) x ----------------RL i
DC-Restore
When the ISL59830A is AC-coupled it becomes necessary to restore the DC reference for the signal. This is accomplished with a DC-restore system applied between the capacitive "AC" coupling and the input of the device. Refer to Application Circuit for reference DC-restore solution.
Disable/Power-Down
The ISL59830A can be disabled and its output placed in a high impedance state. The turn-off time is around 25ns and the turn-on time is around 200ns. When disabled, the amplifier's supply current is reduced to 0.9mA typically, thereby effectively eliminating the power consumption. The amplifier's power-down can be controlled by standard TTL or CMOS signal levels at the EN and PD pins. The applied logic signal is relative to VS- pin. Letting the EN and PD pins float or applying a signal that is less than 0.8V above VS- will enable the amplifier. The amplifier will be disabled when the signal at EN pin is 2V above VS-. The amplifier must be disabled (EN pin is high) whenever the charge pump is disabled (PD pin is high). EN and PD pins should be connected together to allow amplifier and charge pump to enable/disable simultaneously.
for sinking:
PD MAX = V S x I SMAX + ( V OUT i - V S ) x I LOAD i
Where: VS = Supply voltage ISMAX = Maximum quiescent supply current VOUT = Maximum output voltage of the application RLOAD = Load resistance tied to ground ILOAD = Load current i = Number of output channels By setting the two PDMAX equations equal to each other, we can solve the output current and RLOAD to avoid the device overheat.
Output Drive Capability
The ISL59830A does not have internal short-circuit protection circuitry. A short-circuit current of 80mA sourcing and 150mA sinking for the output is connected to half way between the rails with a 10 resistor. If the output is shorted indefinitely, the power dissipation could easily increase such that the part will be destroyed. Maximum reliability is maintained if the output current never exceeds 40mA, after which the electro-migration limit of the process will be 13
FN6233.3 September 26, 2006
ISL59830A
Power Supply Bypassing and Printed Circuit Board Layout
Strip line design techniques are recommended for the input and output signal traces. As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7F tantalum capacitor in parallel with a 0.1F ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split-internal supplies are to be used. In this case, the VSpin becomes the negative supply rail. For good AC performance, parasitic capacitance should be kept to a minimum. Use of wire-wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance can result in compromised performance. Minimizing parasitic capacitance at the amplifier's inverting input pin is also very important.
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FN6233.3 September 26, 2006
ISL59830A Shrink Small Outline Plastic Packages (SSOP) Quarter Size Outline Plastic Packages (QSOP)
N INDEX AREA E -B1 2 3 0.25 0.010 h x 45 L GAUGE PLANE H 0.25(0.010) M BM
M16.15A
16 LEAD SHRINK SMALL OUTLINE PLASTIC PACKAGE (0.150" WIDE BODY) INCHES SYMBOL A A1
SEATING PLANE -AD -CA
MILLIMETERS MIN 1.55 0.102 1.40 0.20 0.191 4.80 3.81 MAX 1.73 0.249 1.55 0.31 0.249 4.98 3.99 NOTES 9 3 4 5 6 7 8 Rev. 2 6/04
MIN 0.061 0.004 0.055 0.008 0.0075 0.189 0.150
MAX 0.068 0.0098 0.061 0.012 0.0098 0.196 0.157
A2 B C D
A1 0.10(0.004) A2 C
E e H h L
e
B 0.17(0.007) M C AM BS
0.025 BSC 0.230 0.010 0.016 16 0 8 0.244 0.016 0.035
0.635 BSC 5.84 0.25 0.41 16 0 6.20 0.41 0.89
NOTES: 1. Symbols are defined in the "MO Series Symbol List" in Section 2.2 of Publication Number 95. 2. Dimensioning and tolerancing per ANSI Y14.5M-1982. 3. Dimension "D" does not include mold flash, protrusions or gate burrs. Mold flash, protrusion and gate burrs shall not exceed 0.15mm (0.006 inch) per side. 4. Dimension "E" does not include interlead flash or protrusions. Interlead flash and protrusions shall not exceed 0.25mm (0.010 inch) per side. 5. The chamfer on the body is optional. If it is not present, a visual index feature must be located within the crosshatched area. 6. "L" is the length of terminal for soldering to a substrate. 7. "N" is the number of terminal positions. 8. Terminal numbers are shown for reference only. 9. Dimension "B" does not include dambar protrusion. Allowable dambar protrusion shall be 0.10mm (0.004 inch) total in excess of "B" dimension at maximum material condition. 10. Controlling dimension: INCHES. Converted millimeter dimensions are not necessarily exact.
N
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com 15
FN6233.3 September 26, 2006

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